DD5-c9-高频电感和变压器的设计讲解课件

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1、Chapter 9：Design of High-Frequency Inductors and Transformers9-1 Introduction9-2 Basics of Magnetic Design9-4 Area-Product Method9-5 Design Example of an Inductor9-6 Design Example of a Transformer for a Forward Converter9-7 Loss mechanisms in magnetic circuitsFrom Reference 2-First Course on Power

2、Electronics19-1 Introduction High-frequency inductors and transforms are generally not available off-the-shelf,and must be designed based on the application specifications.So far,we have mostly considered analysis.Design is more challenging,and is partly an art.In this chapter,a simple and a commonl

3、y used approach called Area-Product method is presented,where the thermal considerations are ignored.(A detailed design discussion is presented in Chapter 30 of the Textbook)29-2 BASICS OF MAGNETIC DESIGN In designing high frequency inductors and transforms,a designer is faced with countless choices

4、,including:Core materials(permeability is dependent of materials)Core shape(some offer better thermal conduction whereas others offer better shielding to stray flux)Cooling methods(natural convection versus forced cooling)Losses(lower losses offer higher efficiency at the expense of higher size and

5、weight)31 Design consists of:(1)Selecting appropriate core material,geometry,and size(2)Selecting appropriate copper winding parameters:wire type,size,and number of turns.Core(double E)Winding Bobbin Assembled core and winding42 Overview of core material:(1)Iron-based alloy laminated cores(often ter

6、med magnetic steels):comprised of alloys principally of iron and small amounts of other elements,including:Various compositions Fe-Si(few percent Si)Fe-Cr-Mn Important properties lower Resistivity=(10100)Cu large values of saturation flux density Bs=11.8T Used in low-frequency applications.5(2)Powde

7、red iron alloy cores:consist of small iron particles electrically isolated from each other.Various compositions Fe-Si(few percent Si)Fe-Cr-Mn Important properties have larger effective resistivity than laminated cores6(3)Ferrite cores Various compositions Iron oxides Fe-Ni-Mn oxides Important proper

8、ties Resistivity very large(insulator)-no ohmic losses and hence skin effect problems at high frequencies.Bs=0.3T(T=tesla)7Core materials comparison83 Magnetic core shapes Ferrite cores available as U,E,and I shapes as well as pot cores and toroids.Laminated(conducting)materials available in E,U,and

9、 I shapes as well as tape wound toroids and C-shapes.insulating layer magnetic steel lamination91011 Open geometries such as E-core make for easier fabrication and better thermal conduction but more stray flux and hence potentially more severe EMI problems.Closed geometries such as pot cores make fo

10、r more difficult fabrication and worse thermal conduction but much less stray flux and hence EMI problems.124 Two basic quantities need being calculated in design-optimization problems:The peak flux density Bmax in the magnetic core(we most not exceed the allowed flux density of the material.BmaxBsa

11、t)to limit core losses,andThe peak current density Jmax in the winding conductors(wine must thick enough to carry current without overheating)to limit conduction losses.In general,JmaxBmax25 A pot core 2616,which is shown in Fig.9-4 for a laboratory experiment,has the core Area Acore=93.1 mm2 and th

12、e window Area Awindow=39mm2.Therefore,we will select this core,which has an Area-Product Ap=93.139=3631mm4 3583mm4.Soluction:3 selecting core shape to ensure practical Apcalculated Ap.26Soluction:4 calculating N.Winding wire cross sectional area Acond=Irms/Jmax=5.0/6.0=0.83mm2.We will use five stran

13、ds of American Wire Gauge AWG 25 wires 3,each with a cross-sectional area of 0.16mm2,in parallel.Soluction:5 selecting Acond.27Soluction:6 calculating lg.289-6 DESIGN EXAMPLE OF A TRANSFORMER FOR A FORWARD CONVERTER The required electrical specifications for the transformer in a Forward converter ar

14、e as follows:fs=100kHz and V1=V2=V3=30V.Assume the rms value of the current in each winding to be 2.5 A.We will choose the following values for this design:Bmax=0.25T,Jmax=5A/mm2,kw=0.5,kconv=0.5.29Soluction:1 Calculating Ap.Soluction:2 selecting core shape to ensure practical Apcalculated ApSelect

15、pot core 2213,Acore=63.9mm2,Awindow=29.2mm2,and therefore Ap=1866mm41800mm4.30Soluction:3 calculating N31Use three strands of AWG 25 wires 3,each with a cross-sectional area of 0.16mm2,in parallel for each winding.Soluction:4 selecting Acond329-7 Loss mechanisms in magnetic circuits The size of a ma

16、gnetic component is often determined by loss.Generally,the losses can be divided into 2 components:winding associated loss and core associated loss.331 Winding loss At low frequency(including dc),winding loss is just due to the dc resistance in the winding and is easy to calculate.Pdiss=(irms)2Rwire

17、At higher frequency,there are additional effect we must consider of:skin effect and proximity effect.34Skin effectSkin effect is the“self-shielding”effect of conductors:Due to eddy currents generated by changes in magnetic field of an ac current,the fields and currents may not penetrate inside a con

18、ductor at high frequency.I(t)H(t)I(t)J(t)J(t)0Eddy currentsraa(a)(b)(c)Time-varying current i(t)Magnetic fields H(t)Eddy currents35According to Lenzs law,magnetic fields within the core induce currents(“eddy currents”)to flow within the core.The eddy currents flow such that they tend to generate a f

19、lux which opposes changes in the core flux(t).The eddy currents tend to prevent flux from penetrating the core.36Eddy Currents Increase Winding Losseseddy currents cause a nonuniform current density in the conductor.Effective resistance of conductor increased over dc value.For sinusoidal currents:cu

20、rrent density is an exponentially decaying function of distance into the conductor,with characteristic length known as the penetration depth or skin depth.37Numerical example using copper at 100C.Frequency50Hz5kHz20kHz500kHzSkin Depth10.6mm1.06mm0.53mm0.106mmFor copper at room temperature:38 So,if w

21、e need to carry high frequency current,wine of radiusis not useful,since the current will be carried only on the surface of the wine.The solution to this problem is to parallel isolated wire of thickness.Each layer carries net current i(t).40Proximity effect causes significant power loss in the wind

22、ings of high-frequency transformers and ac inductors,especially in multi-layer windings.The solution to minimize proximity losses is:In inductors,windings can be with single-layer construction.In transforms,windings can be interleaved and avoided highs of layer.41Example:a two-winding transformerPri

23、mary turns are wound in three layers,assume that each layer is one turn.The secondary is a similar three-layer winding.Each layer carries net current i(t).Portions of the windings that lie outside of the core window are not illustrated.Each layerhas thickness h.42(1)Distribution of currents on surfa

24、ces of conductors:Skin effect causes currents to concentrate on surfaces of conductors Surface current inducesequal and opposite currenton adjacent conductor Net conductor current isequal to i(t)for each layer,since layers are connected in series Circulating currents within layers increase with the

25、numbers of layers43(2)Estimating proximity loss:high-frequency limitThe current i(t)having rms value I is confined to thickness on the surface of layer 1.Hence the effective“ac”resistance of layer 1 is:Rac=(h/)RdcThis induces copper loss P1 in layer 1:P1=I2Rac44Power loss P2 in layer 2 is:P2=P1+4P1=

26、5P1Power loss P3 in layer 3 is:P3=(22+32)P1=13P145Add up losses in each layer:Compare with dc copper loss:If foil thickness were H=,then at dc each layer would produce copper loss P1.The copper loss of M-layer winding would be Pdc=I2MRdcSo the proximity effect increases the copper loss by a factor o

27、f:46The solution to minimize proximity losses is:In inductors,windings can be with single-layer construction.In transforms,windings can be interleaved and avoided highs of layer.47(3)Two-winding transformer MMF diagramWinding layoutMMF diagram(a)without proximity effect48(b)with proximity effect49(c

28、)Interleaving the windings:MMF diagramGreatly reduces the peak MMF,leakage flux,and proximity losses502 Core loss=Eddy current loss+hysteresis lossSkin effectdB/dt through core generates voltage which drive eddy currents around core,these eddy currents flow such that they tend to generate a flux whi

29、ch oppose change core flue!xdx-xLdwBsin(wt)xyzEddy current flow path51xdx-xLdwBsin(wt)xyzEddy current flow pathTime-varying magnetic fields B(t)Eddy currents Secondary magnetic fields that oppose the applied magnetic field.52Eddy Currents effects(1)Cause eddy current losses!(2)Cause the flux to be r

30、ejected from the core!The total magnetic field in the core decays exponentially with the distance into the core.BB/2.7yskin depth:53 The solution to this problem is to increase the resistivity of the core(adding small percentage of silicon to the iron),and to use core that made from stacks of many t

31、hin laminations.Magnetic steel laminationInsulator0.05 tt(typically 0.3 mm)54Magnetic steel laminationInsulator0.05 tt(typically 0.3 mm)Cores made from conductive magnetic materials must be made of many thin laminations.Lamination thickness skin depth.Stacking factor kstack=t/(t+0.05t)55Hysteresis l

32、ossBHMinor hysteresis loopBs-BsCore losses(hysteresis,eddy currents)increase as B2(or greater)Area encompassed by hysteresis loop equals work done on material during one cycle of applied ac magnetic field.Area times frequency equals power dissipated per unit volume.56Typical waveforms of flux density,B(t)versus time,in an inductor.Only Bac contributes to hysteresis loss.tBac0t0B(t)BavgBacFigure 30-1 Magnetic flux density waveforms57